Title | DSP OHT 1 Cheat Sheet |
---|---|
Author | Syed Shaharyaar Hussain |
Course | Signals and systems |
Institution | National University of Sciences and Technology |
Pages | 2 |
File Size | 478.8 KB |
File Type | |
Total Downloads | 49 |
Total Views | 141 |
This is formula sheet compilation by my batch mates Usama Mirza and Hamza Chippa for the course of Digital Signal Processing....
∞
If ROC contains unit circle then the system is stable If ROC contains infinity then the system is causal ROC cannot contain any poles ROC must be a connected region
x[n] = ∑ x[k]δ[n − k] k=− ∞ ∞
u[n] = ∑ δ[n − k] k=0
δ [n] = u[n] − u[n − 1] N = 2πk ω I deal delay system : y [n] = x [n − nd ] 1 M1 +M2 +1
M oving Average System : y [n] =
Sampling ∞
s(t) = ∑ δ (t − nT s )
M2
n=− ∞
∑ x [n − k ]
∞
∞
xs (t) = xc (t)s(t) = ∑ xc(t)δ(t − nT s) = ∑ xc(nT s)δ(t − nT s)
k=− M 1
n=− ∞
n=− ∞
n
Accumulator System : y[n] = ∑ x[k]
S (jΩ) =
k=− ∞
2π Ts
C ompressor System : y [n] = x[Mn]
∞
∑ δ(Ω − kΩ s), Ω s = 2π /T
s
k=− ∞ ∞
X s (jΩ) =
1 X (jΩ) 2π c
Finite Impulse Response (FIR) Infinite Impulse Response (IIR)
1 * S(jΩ) = T s ∑ X c(j(Ω − kΩ s)) k=− ∞
Memoryless: Depends only on present value on n h[n] = 0, for n =/ 0 Causal: Doesn’t depend on future values of n h[n] = 0, for n < 0
Ωs ≥ 2Ω N , Ω N is the greatest frequency in x c(t)
Stable: Finite output for finite input ∞
∑ ∣h[n] ∣ has to be finite
n=− ∞
Aliasing if Nyquist’s criteria not satisfied
Linear System: A x1 [n] + B x2 [n] → Ay 1 [n] + By 2[n] Time Invariant: x[n − no ] → y [n − no ]
Convolution:
Original signal can be recovered using a low pass filter
∞
x[n] * h[n] = ∑ x [k]h[n − k ] k= −∞
x[n] * δ[n] = x[n], x[n] * δ[n − k] = x[n − k] Complex exponentials are eigenfunctions of LTI Systems H(ej⍵ ) is the eigenvalue of an LTI System ∞
Fourier Transform: X (ejω ) = ∑ x[n]e − jωn (Periodic with period = 2𝜋) n= −∞
Synthesis Equation: x[n] =
1 2π
∫ X(e j ω)e j ωndω 2π
Fourier Series
Fourier exists if x[n] is absolutely summable
ak =
∞
Z-Transform: X (z) = ∑ x[n]z −n n= −∞
Synthesis Equation: x[n] =
Finite signal
Right sided signal
Left sided signal
Double sided signal
1 N
∑ x[n]e −jkω on Periodic with Period N n=
x[n] = ∑ ak ejkωo n 1 2πj
k=
∮ X (z )z n −1 dz C
Entire z plane except possibly z=0 or z=∞
Table 5: Properties of the Discrete-Time Fourier Transform 1 Z X(ejω ) ej ωndω x [n] = 2π 2π +∞ X x [n]e−jωn X(ejω ) =
Table 2: Properties of the Discrete-Time Fourier Series X X ak ejk (2π/N )n x [n ] = ak ejkω0 n = k=
1 X
ak =
Property
Time Scaling
x [n]e−jkω0 n =
n=
1 X
N
x [n]e−jk (2π/N )n
Fourier series coefficients
ak bk
Periodic with period N and fundamental frequency ω 0 = 2π/N
Ax [n] + By [n] x [n − n0 ] ejM (2π/N)n x [n] x ∗ [n ] x [−n] x [n/m] if n is a multiple of m x (m) [n] = 0 if n is not a multiple of m
Periodic with period N
Aak + Bbk ak e−jk (2π/N )n 0 ak−M ∗ a−k a−k viewed as 1 ak periodic with m period mN
X
Aperiodic Signal
!
Convolution Multiplication
x [n]y[n]
Differencing in Time
x [r]y[n − r]
Nak bk X
x [n]y[n]
Fourier transform
x [n] y[n] ax [n] + by[n] x [n − n0 ] ej ω0n x [n] x ∗ [n] x [−n] x [n/k ], if n = multiple of k x (k) [n] = 0, if n 6= multiple of k x [n] ∗ y[n]
Time Expansions
r=hNi
Multiplication
Property
Linearity Time-Shifting Frequency-Shifting Conjugation Time Reversal
(periodic with period mN )
Periodic Convolution
x [n] − x[n − 1] n X x[k]
Accumulation
Running Sum
x [n] − x [n − 1] n X finite-valued and x[k] periodic only if a = 0 0 k=−∞
Conjugate Symmetry for Real Signals
x [n] real
Real and Even Signals
x [n] real and even
Real and Odd Signals
x [n] real and odd
Even-Odd Decomposition of Real Signals
(1 − e−jk (2π/N ) )ak 1 ak (1 − e−jk (2π/N ) ) ∗ a = a k −k ℜe{ak } = ℜe{a−k } ℑm{ ak } = −ℑm{ a−k } | ak | = | a−k | 0) or ∞ (if m < 0)
Differentiation in the z-Domain
Pn
1 1−z −1 X(z)
nx[n]
z) −z dX( dz
k=−∞ x[k]
Initial Value Theorem If x[n] = 0 for n < 0, then x[0] = limz →∞ X(z)
π
+∞ X
π j
+∞ X
Fourier series coefficients (if periodic) ak 2πm = N 1, k = m, m ± N, m ± 2N , . . . 0, otherwise irrational ⇒ The signal is aperiodic ω0 = 2πm N 1 k = ±m, ±m ± N, ±m ± 2N, . . . 2, ak = 0, otherwise ω0 irrational ⇒ The signal is aperiodic 2π ω0 = 2πr N1 k = r, r ± N, r ± 2N , . . . 2j , 1 − 2j = , k = −r, −r ± N, −r ± 2N, . . . 0, otherwise ω0 irrational ⇒ The signal is aperiodic 2π 1, k = 0, ±N, ±2N , . . . 0, otherwise
(a)
ω0 ak
{δ(ω − ω0 − 2πl) + δ(ω + ω0 − 2πl)} (b) (a) {δ(ω − ω0 − 2πl) − δ(ω + ω0 − 2πl)}
ak
l=−∞
(b) 2π
+∞ X
δ(ω − 2πl)
Periodic square wave 1, |n| ≤ N1 0, N1 < |n| ≤ N/2 and x[n + N ] = x[n] +∞ X δ[n − kN ] x[n] =
2π
+∞ X
2πk ak δ ω − N
k=−∞
2π N
k=−∞
ak =
k=−∞
δ ω−
2πk N
1 1 − ae−jω sin[ω (N1 + 1 )] 2 sin(ω/2) 1, 0 ≤ |ω| ≤ W X(ω) = 0, W < |ω| ≤ π X(ω)periodic with period 2π
an u[n], |a| < 1
1, |n| ≤ N1 0, |n| > N1 sinc Wπn 0 0
9. [cos ω0n]u[n]
1−[cos ω0 ]z−1 1−[2 cos ω0 ]z−1 +z −2
|z| > 1
At least the intersection of R and |z| > 1
10. [sin ω0n]u[n]
[sin ω0 ]z−1 −2 1−[2 cos ω0 ]z−1 +z
|z| > 1
11. [r n cos ω0n]u[n]
1−[r cos ω0 ]z−1 −2 1−[2r cos ω0 ]z −1 +r 2 z
|z| > r
12. [r n sin ω0n]u[n]
[ r sin ω0 ] z 1−[2r cos ω0 ]z −1 +r 2 z−2
|z| > r
R
−1
Useful Infinite Summation Identities (|a| < 1) ∞ X k=0 ∞
X
ak =
1 1−a
kak =
a 2
(1 − a) X 2 k a2 + a k a = (1 − a)3 k=0 k=0 ∞...